France



I.Introduction&lt;br/&gt;Hybrid magnetic bearings (HMBs) have several merits, such as no friction and abrasions, no lubrication and no sealing, high speed, high precision and long life. In HMBs, the permanent magnet is adopted to generate bias flux for the low power consumption and small volume. However, in existing HMBs, several suspension poles are designed in the same stator core. The suspension force is generated by the interaction of the bias flux and control flux. The HMB of this structure realizes the radial two-degree-of-freedom (2-DOF) suspension in one stator core, especially when the rotor is deviated from unbalance position, the suspension force coupling in the X-Y direction is severe and the control is complicated. To compensate for this deficiency, a novel DC HMB with crossed poles is studied. The suspension poles in the X and Y direction are designed different stator cores. Therefore, it can solve the radial 2-DOF coupling of traditional four-pole HMBs and simplify the control. A simple mathematical models are presented, which can make the maximum magnetic levitation force in the X and Y directions. The nonlinearity of suspension forces and the coupling of electromagnetic among this four-pole magnetic bearing are analyzed by MagNet 3D. The finite element simulation is carried out to verify the theoretical analysis.&lt;br/&gt;II.Configuration and Suspension Principle&lt;br/&gt;The configuration and magnetic circuit of a novel DC HMB with crossed poles are presented in Fig. 1. As shown in Fig. 1(a), the main parts of this HMB are two slice stators, namely X-stator and Y-stator, axial magnetized permanent magnets and two slice rotor irons. Two symmetrical suspension poles in the X direction are evenly distributed along the circumference of X-stator, and the suspension poles in the Y direction are crossed in the Y-stator. Radial control windings are wound on each stator.&lt;br/&gt;The magnetic circuit of radial suspension control flux and static bias flux is represented in Fig. 2(b). The solid lines denote the static bias flux generated by the permanent magnets. The dotted lines describe the radial suspension control flux generated by radial control current. If the rotor irons are displaced from the balance position in the radial position by the radial disturbances, the fluxes between the magnetic flux and the bias flux are overlapped, which results in force to bring the rotor to the radial balance position.&lt;br/&gt;According to the equivalent magnetic circuit method, the radial suspension forces in the X and the Y directions are deduced as follows:&lt;br/&gt;&lt;i&gt;F&lt;sub&gt;j&lt;/sub&gt;&lt;/i&gt;=&lt;i&gt;F&lt;sub&gt;pm&lt;/sub&gt;&lt;/i&gt;+&lt;i&gt;k&lt;sub&gt;ij&lt;/sub&gt;&lt;/i&gt;×&lt;i&gt;ij&lt;/i&gt;(1)&lt;br/&gt;where the subscript “&lt;i&gt;j&lt;/i&gt;” denotes &lt;i&gt;x&lt;/i&gt; and &lt;i&gt;y&lt;/i&gt;. &lt;i&gt;F&lt;/i&gt;&lt;i&gt;&lt;sub&gt;pm&lt;/sub&gt; &lt;/i&gt;is the magnetic attraction force produced by the bias flux at the equilibrium position. &lt;i&gt;k&lt;sub&gt;i&lt;/sub&gt;&lt;sub&gt;j&lt;/sub&gt;&lt;/i&gt; is the radial force-current stiffness.&lt;i&gt; F&lt;/i&gt;&lt;i&gt;&lt;sub&gt;pm&lt;/sub&gt;&lt;/i&gt; and &lt;i&gt;k&lt;sub&gt;i&lt;/sub&gt;&lt;/i&gt;&lt;i&gt;&lt;sub&gt;j &lt;/sub&gt;&lt;/i&gt;can be given as:&lt;br/&gt;&lt;i&gt;F&lt;sub&gt;pm&lt;/sub&gt;&lt;/i&gt;=-&lt;i&gt;S&lt;/i&gt;×&lt;i&gt;μ0&lt;/i&gt;×&lt;i&gt;F&lt;sub&gt;m&lt;/sub&gt;&lt;/i&gt;×&lt;i&gt;F&lt;sub&gt;m&lt;/sub&gt;&lt;/i&gt;÷&lt;i&gt;g&lt;sup&gt;3&lt;/sup&gt;&lt;/i&gt;&lt;br/&gt;&lt;i&gt;K&lt;sub&gt;ij&lt;/sub&gt;&lt;/i&gt;=2&lt;i&gt;S&lt;/i&gt;×&lt;i&gt;μ&lt;sub&gt;0&lt;/sub&gt;&lt;/i&gt;×&lt;i&gt;F&lt;sub&gt;m&lt;/sub&gt;&lt;/i&gt;×&lt;i&gt;N&lt;/i&gt;÷&lt;i&gt;g&lt;sup&gt;2&lt;/sup&gt;&lt;/i&gt;(2)&lt;br/&gt;where &lt;i&gt;F&lt;sub&gt;m&lt;/sub&gt;&lt;/i&gt; is the magnetomotive force. &lt;i&gt;μ&lt;/i&gt;&lt;sub&gt;0&lt;/sub&gt; is vacuum permeability. &lt;i&gt;S&lt;/i&gt; is radial magnetic pole area. &lt;i&gt;g&lt;sub&gt; &lt;/sub&gt;&lt;/i&gt;is radial air gap length. &lt;i&gt;N&lt;/i&gt; is number of radial control coils.&lt;br/&gt;III.Models, Design and Analysis&lt;br/&gt;Based on above-mentioned analysis, electromagnetic performance of the presented HMB is manufactured by the MagNet software. The prototype is simulated to analyze the electromagnetic performance by the three-dimensional finite element method, and the different simulation cases are given in Fig. 2. Fig. 2(a) shows the distribution of the bias flux. The radial air-gap magnetic flux density of each pole is 0.6T symmetrically. In Fig. 2(b), the radial control winding in the X direction is electrified with 3A current, and the control flux density distribution in the X direction is generated. It can be seen from Fig. 2(c) that there is an increase of air-gap flux in the positive X direction and a decrease in the negative X direction by the superposition of the control flux in the X direction and bias flux. Therefore, only the suspension force in the X direction is produced.&lt;br/&gt;To verify the correctness of the mathematical models, the control current is applied to generate radial suspension force only in the positive X direction. The relationships between the suspension force and control current are shown in Fig. 2(d). The currents change from 0 to 3 A. The maximum suspension force reaches 260 N. It can be seen that the finite element simulation results are in good agreement with the theoretical values, and there is a linear force-current relationships.&lt;br/&gt;IV. Conclusion&lt;br/&gt;This paper aims to construct a novel DC HMB with crossed poles to simplify the structure, obtain the maximum bearing capacity and solve the radial two-degree-of-freedom coupling. The simulation results have shown that the suspension forces produced by the crossed poles have better linearity around the balance position and no movement. There is no coupling of two directions for the independent magnetic circuit. The research results verify the correctness of magnetic circuit, suspension mechanism and mathematical model.

**References:**

&lt;br/&gt;[1]D. Ning, H. Kai, and J. Long, &quot;Review on High Speed Permanent Magnet Machines Including Design and Analysis Technologies,&quot; in &lt;i&gt;Proceedings of the CSEE&lt;/i&gt;, vol. 34, no. 27, pp. 4640-4653, Sep,  2014.&lt;br/&gt;[2]J. Ju, H. Zhu and C. Zhao, &quot;Radial Force-Current Characteristic Analysis of Three-Pole Radial-Axial HMB,&quot; &lt;i&gt;2016 IEEE Vehicle Power and Propulsion Conference (VPPC)&lt;/i&gt;, Hangzhou, 2016, pp. 1-6.

**Images:**

![](https://assets.underline.io/uploads/markdown_image/1/image/b086123141f2db12e85d7de06a7be696.jpg)
Fig. 1. The configuration and magnetic flux path of the proposed HMB.

![](https://assets.underline.io/uploads/markdown_image/1/image/2114063a67fc96a8d89fdd14022a9115.jpg)
Fig. 2. Flux distribution and the force-current relationships. (a) Bias flux. (b) Control flux. (c) Resultant flux. (d) Force-current relationship.

INTERMAG 2021

 Modeling and Electromagnetic Performance Analysis of the Novel DC Hybrid Magnetic Bearing with Crossed Poles

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I.Introduction Hybrid magnetic bearings (HMBs) have several merits, such as no friction and abrasions, no lubrication and no sealing, high speed, high precision and long life. In HMBs, the permanent magnet is adopted to generate bias flux for the low power consumption and small volume. However, in existing HMBs, several suspension poles are designed in the same stator core. The suspension force is generated by the interaction of the bias flux and control flux. The HMB of this structure realizes the radial two-degree-of-freedom (2-DOF) suspension in one stator core, especially when the rotor is deviated from unbalance position, the suspension force coupling in the X-Y direction is severe and the control is complicated. To compensate for this deficiency, a novel DC HMB with crossed poles is studied. The suspension poles in the X and Y direction are designed different stator cores. Therefore, it can solve the radial 2-DOF coupling of traditional four-pole HMBs and simplify the control. A simple mathematical models are presented, which can make the maximum magnetic levitation force in the X and Y directions. The nonlinearity of suspension forces and the coupling of electromagnetic among this four-pole magnetic bearing are analyzed by MagNet 3D. The finite element simulation is carried out to verify the theoretical analysis. II.Configuration and Suspension Principle The configuration and magnetic circuit of a novel DC HMB with crossed poles are presented in Fig. 1. As shown in Fig. 1(a), the main parts of this HMB are two slice stators, namely X-stator and Y-stator, axial magnetized permanent magnets and two slice rotor irons. Two symmetrical suspension poles in the X direction are evenly distributed along the circumference of X-stator, and the suspension poles in the Y direction are crossed in the Y-stator. Radial control windings are wound on each stator. The magnetic circuit of radial suspension control flux and static bias flux is represented in Fig. 2(b). The solid lines denote the static bias flux generated by the permanent magnets. The dotted lines describe the radial suspension control flux generated by radial control current. If the rotor irons are displaced from the balance position in the radial position by the radial disturbances, the fluxes between the magnetic flux and the bias flux are overlapped, which results in force to bring the rotor to the radial balance position. According to the equivalent magnetic circuit method, the radial suspension forces in the X and the Y directions are deduced as follows: Fj=Fpm+kij×ij(1) where the subscript “j” denotes x and y. Fpm is the magnetic attraction force produced by the bias flux at the equilibrium position. kij is the radial force-current stiffness. Fpm and kij can be given as: Fpm=-S×μ0×Fm×Fm÷g3 Kij=2S×μ0×Fm×N÷g2(2) where Fm is the magnetomotive force. μ0 is vacuum permeability. S is radial magnetic pole area. g is radial air gap length. N is number of radial control coils. III.Models, Design and Analysis Based on above-mentioned analysis, electromagnetic performance of the presented HMB is manufactured by the MagNet software. The prototype is simulated to analyze the electromagnetic performance by the three-dimensional finite element method, and the different simulation cases are given in Fig. 2. Fig. 2(a) shows the distribution of the bias flux. The radial air-gap magnetic flux density of each pole is 0.6T symmetrically. In Fig. 2(b), the radial control winding in the X direction is electrified with 3A current, and the control flux density distribution in the X direction is generated. It can be seen from Fig. 2(c) that there is an increase of air-gap flux in the positive X direction and a decrease in the negative X direction by the superposition of the control flux in the X direction and bias flux. Therefore, only the suspension force in the X direction is produced. To verify the correctness of the mathematical models, the control current is applied to generate radial suspension force only in the positive X direction. The relationships between the suspension force and control current are shown in Fig. 2(d). The currents change from 0 to 3 A. The maximum suspension force reaches 260 N. It can be seen that the finite element simulation results are in good agreement with the theoretical values, and there is a linear force-current relationships. IV. Conclusion This paper aims to construct a novel DC HMB with crossed poles to simplify the structure, obtain the maximum bearing capacity and solve the radial two-degree-of-freedom coupling. The simulation results have shown that the suspension forces produced by the crossed poles have better linearity around the balance position and no movement. There is no coupling of two directions for the independent magnetic circuit. The research results verify the correctness of magnetic circuit, suspension mechanism and mathematical model.

**References:**

 [1]D. Ning, H. Kai, and J. Long, "Review on High Speed Permanent Magnet Machines Including Design and Analysis Technologies," in Proceedings of the CSEE, vol. 34, no. 27, pp. 4640-4653, Sep, 2014. [2]J. Ju, H. Zhu and C. Zhao, "Radial Force-Current Characteristic Analysis of Three-Pole Radial-Axial HMB," 2016 IEEE Vehicle Power and Propulsion Conference (VPPC), Hangzhou, 2016, pp. 1-6.

**Images:**

![](https://assets.underline.io/uploads/markdown_image/1/image/b086123141f2db12e85d7de06a7be696.jpg)
Fig. 1. The configuration and magnetic flux path of the proposed HMB.

![](https://assets.underline.io/uploads/markdown_image/1/image/2114063a67fc96a8d89fdd14022a9115.jpg)
Fig. 2. Flux distribution and the force-current relationships. (a) Bias flux. (b) Control flux. (c) Resultant flux. (d) Force-current relationship.

poster

1. Induction: The accurate estimation of the harmonic losses caused by the zig-zag leakage flux which occupies a high proportion of stray losses is of great significance in the efficiency calculation as well as the optimization design for the wet submersible induction machine [1]. To precise estimate the zig-zag leakage flux losses at the nominal load, it is necessary to determine losses induced by a particular order of the air-gap flux density harmonic. 2. Analysis and Calculation: In this paper, a two-dimensional finite element method is presented to separate zig-zag leakage flux losses produced by the stator slot harmonic, rotor slot harmonic and interaction harmonic between them, respectively. The air-gap magnetic flux density is decomposed by the two-dimensional fast Fourier transform at a sampling frequency of 5000 Hz. The hybrid excited virtual permanent magnet harmonic machine model is applied to reconstruct the air-gap magnetic field and excited the stator and rotor separately, in which the iron core node magnetic flux density is extracted and decomposed [2]. Each node harmonic iron loss is acquired through the modified Bertotti’s iron loss model with the consideration of high frequency power losses as a function of the magnetic flux density. The losses caused by a single harmonic are obtained by subtracting the losses resulted from the hybrid excitation [3]. Fig. 1(a) shows rotor iron losses density distribution induced by the -17th harmonic, which denotes the first order stator slot harmonic. The rotor is equipped with the closed slot because of the machine’s water-filled operating environment, where the mixed mesh subdivision through triangular mesh and rectangular mesh are employed. It can be seen in Fig. 1(a) that the -17th harmonic penetrates into the rotor surface where the mapped mesh exists. Meanwhile, Fig. 1(b) and Fig. 1(c) display rotor bar and stator winding eddy-current density distributions respectively, where the current density engendered by the -17th harmonic close to the air gap is higher than the rest in other positions. 3. Results: The zig-zag leakage flux losses calculated includes the surface and pulsation losses in the stator and rotor as well as eddy-current losses in the stator winding and squirrel cage. Different proportion of losses caused by corresponding harmonics have important reference for the optimization of the power density of the machine. Table I displays the losses caused by the first and second order stator slot harmonics, together with the first order rotor slot harmonic (-20th and 22nd). In Table I, ‘Nan’ expresses that the corresponding values are small or approach zero. It can be represented that the losses reduce with the order of harmonic, therefore, the iron losses in the stator can be neglected. Meanwhile, the rotor losses generated by the rotor slot harmonic is not listed in the table, because the rotor slot harmonic rotates synchronously with the rotor itself. It can be concluded that the eddy-current losses in the squirrel cage caused by -17th harmonic account for the largest proportion among the overall zig-zag leakage flux losses. Hence, to improve the power density of the machine, effective measures (e.g. rotor skew, semimagnetic wedge) can be taken to reduce the -17th harmonic. The method shown in this paper separates the zig-zag leakage flux harmonic losses and lays a fundamental for the machine design as well as the optimization.

**References:**

[1] R. Hagen, T. Knopik, and A. Binder, IEEE Int. Elect. Mach & Drives Conf., p. 1325-1330 (2009) [2] C. Di, I. Petrov, and J. J. Pyrhönen, IEEE Trans. Magn., Vol. 54, p. 1-12 (2018) [3] C. Di, I. Petrov, and J. J. Pyrhönen, IEEE Access, Vol. 7, p. 27746–27755 (2019)

**Images:**

![](https://assets.underline.io/uploads/markdown_image/1/image/c851afdc272d06b04905972692e636a5.jpg)
Fig. 1 Losses density and current density distributions produced by -17th harmonic at the nominal load. (a) Rotor iron losses. (b) Rotor bar eddy-current. (c) Stator winding eddy-current.

![](https://assets.underline.io/uploads/markdown_image/1/image/44204e85ef9b8db76828a38e27b94f87.jpg)
Table I 
Main Harmonic Amplitude and Zig-Zag Leakage Losses

 Calculation and Decomposition of Zig-Zag Leakage Flux Losses in a Wet Submersible Induction Machine by the Virtual Permanent Magnet Harmonic Machine Model

I. INTRODUCTION In recent years, due to the merits of easy thermal management, alleviated torque ripple and robust rotor, flux reversal permanent magnet (FRPM) machines have attracted more and more attention [1]. However, since the large leakage flux leads to the limitation of its output, a series of novel topologies are proposed, such as the consequent-pole FRPM machine [2], the FRPM machine with asymmetric-stator pole configuration [1] and the FRPM machine with Halbach array magnets in rotor slot (HAM-FRPM) [3], etc. This study presents an analytical sub-domain model for the characteristic evaluation of the HAM-FRPM machine. By dividing the HAM-FRPM machine into seven sub-domains and solving the Maxwell equations in polar coordinate for each region according to the boundary conditions, the vector magnetic potential can be obtained. Subsequently, the radial and tangential flux density can be calculated. Finally, the analytical results are compared with the finite element method (FEM) to verify the accuracy. II. ANALYTICAL SUB-DOMAIN MODEL One 12-stator slot/17-rotor tooth HAM-FRPM machine with double-layer winding is investigated in this paper to verify the proposed method. As shown in Fig.1, the permanent magnet (PM) arrangement in the stator of the HAM-FRPM machine is identical to that of the consequent-pole FRPM machine. In addition, the PMs in each rotor slot are the same, which contain a radially magnetized middle PM and two tangentially magnetized side PMs. In this analytical sub-domain modeling, some essential assumptions have been made in advance: (1) The permeability of iron is regarded as infinite. Also, the relative permeability of PMs and coils is assumed to be 1; (2) The end effect and the magnetic field component on the axial direction are neglected; (3) The geometrical structure side of the HAM-FRPM machine is parallel to either r or θ direction in polar coordinate. As shown in Fig. 2, the HAM-FRPM machine is divided into several regions: stator slot (Region i), stator slot opening (Region l and Region u), PM (Region s and Region g), air gap (Region I) and rotor slot (Region j). Maxwell equation is satisfied in each region as equation (1), which can be expressed as a Poisson equation or a Laplace equation and further solved by the separation of variables method. According to the law of magnetic flux continuity and Neumann condition, the unknown coefficients can de derived. Finally, the radial flux density Br and tangential flux density Bθ can be obtained by (2). where J and M are the current density vector and magnetization vector of magnets, respectively. μ0 is the magnetic permeability of vacuum. III. RESULTS AND DISCUSSION The air gap flux density comparisons between the analytical prediction and FEM results are exhibited in Fig.3-4, which present a good agreement between the analytical results and FEM solution for both radial and tangential air gap flux density. Hence, the proposed analytical model is verified to be used to predict the performances of the HAM-FRPM machines. Fig.5-6 show the back-EMF and torque waveforms, which validate the correctness of analytical model. More detailed derivation and analysis will be shown in the full paper.

**References:**

[1] H. Yang, H. Lin, Z. Q. Zhu, S. Lyu, and Y. Liu, "Design and Analysis of Novel Asymmetric-Stator-Pole Flux Reversal PM Machine," IEEE Transactions on Industrial Electronics, vol. 67, no. 1, pp. 101-114, 2020. [2] Y. Gao, R. Qu, D. Li, J. Li, and G. Zhou, "Consequent-Pole Flux-Reversal Permanent-Magnet Machine for Electric Vehicle Propulsion," IEEE Transactions on Applied Superconductivity, vol. 26, no. 4, pp. 1-5, 2016. [3] K. Yang, F. Zhao, Y. Wang, and Z. Bao, "Consequent-Pole Flux Reversal Permanent Magnet Machine with Halbach Array Magnets in Rotor Slot," IEEE Transactions on Magnetics, pp. 1-1, 2020.

**Images:**

![](https://assets.underline.io/uploads/markdown_image/1/image/df027abcb712ed2aa1b4402da9ebc363.jpg)

![](https://assets.underline.io/uploads/markdown_image/1/image/f005d0617e40bdc8495de330aa1bb659.jpg)

 Analytical Modeling for the Flux Reversal Permanent Magnet Machine with Halbach Array Magnets in Rotor Slot

Permanent magnet synchronous motors have become necessary in several industries that develop home appliances, industrial tools, and electrical vehicles; in addition, there is a growing interest in resolving motor malfunctions. Data provided in [1] show that 41% of motor faults are bearing faults, 37% are stator faults, 10% are rotor faults, and 12% are other faults. One of the main causes of malfunction is rotor eccentricity, wherein the center of the rotor axis deviates from the center of the stator, so that the air gap is not uniform. Static eccentricity, a type of rotor eccentricity, is a condition where the position of the minimum radial air gap is fixed [2]. This can be caused by stator core ovality, incorrect positioning of the stator core, or bearing at commissioning or following a repair, and its level does not change over time [3]. As the magnetic flux density in the air gap is an important characteristic of the machine performance [4] [5], the characteristics of the permanent magnet machine and the impact of rotor eccentricity on the magnetic field distribution must be analyzed. Finite element and analytical methods are employed to design a permanent magnet synchronous motor or perform characteristic analysis. The finite element method (FEM) is a numerical process that can be performed using a commercial tool. However, it is necessary to learn to use each commercial tool and have a disadvantage depending on the experience of the designer for accurate analysis. The analytical method analyzed the electromagnetic field characteristics using Maxwell's equation. Magnetization modeling is applied to the design of the machine using the Fourier series and partial differential equations derived using the magnetic vector potential. It must be preceded by deriving a solution that considers various boundary conditions. Several studies are being conducted because the analytical method can quickly predict the characteristic variation according to the design parameters. This study compared electromagnetic characteristics based on rotor eccentricity using the analytical method. Magnetic flux density, induced voltage, and unbalanced magnetic force were derived using the analytical models. The results were verified by experiments and the FEM. Figure 1(a) shows the experimental setup, and Fig. 1(b) shows the manufactured test motors. An experimental setting was constructed to control rotor eccentricity. To measure the back-EMF at the rated speed, a back-to-back system was constructed, wherein one servo motor and one test motor were arranged successively. In addition, the rotor eccentricity was precisely controlled using two gap sensors. The analysis model was simplified based on several assumptions obtained from the analytical method. Based on the electromagnetic field and perturbation theories, the governing equations of the air-gap region were derived. Furthermore, the relationship between the magnetic vector potential in each region and appropriate boundary conditions was used to obtain undefined coefficients to derive magnetic flux density characteristics in each region. Figures 2(a) and (b) exhibit the magnetic flux density derived using the analytical method and the radial and tangential components with a 25% eccentricity ratio. The induced voltage was derived using the magnetic flux density, and Figs. 2(c) and (d) show the comparison of the induced voltages of the 8-pole 12-slot and 8-pole 9-slot models. The induced voltage of the 8-pole 12-slot model was expressed by each branch of winding because of the symmetry of the winding distribution. The induced voltage of the 8-pole 9-slot model differs in magnitude for each of the three phases owing to the asymmetry of the winding distribution. These no-load characteristics affect the load and reduce the life of the machine. The analytical results were validated by comparing the FEM and experimental results. Detailed results, discussions, and desired effects will be presented in the main paper.

**References:**

[1] J. R. Cameron, W. T. Thomson, and A. B. Dow, “Vibration and current monitoring for detecting airgap eccentricity in large induction motors,” Proc. IEE Electr. Power Appl. B, vol. 133, no. 3, pp. 155–163, May 1986. [2] Q. Zhu, D. Howe, E. Blote, and B. Ackermann, “Instantaneous magnetic field distribution in brushless permanent magnet DC motors, Part I: Open-circuit field”, IEEE Trans. Magn., vol 29, pp. 124-135, Jan. 1993. [3] U. Kim and D. K. Lieu, “Magnetic field calculation in permanent magnet motors with rotor eccentricity: Without slotting effect”, IEEE Trans. Magn., vol. 34, no. 4, pp. 2242-2252, Jul. 1998. [4] A. Rahideh and T. Korakianitis, “Analytical open-circuit magnetic field distribution of slotless brushless permanent magnet machines with rotor eccentricity”, IEEE Trans Magn., vol 47, no. 12, pp. 4791-4808, Jun. 2011. [5] U. Kim and D. K. Lieu, “Effects of magnetically induced vibration force in brushless permanent magnet motors ”, IEEE Trans. Magn., vol. 41, no. 6, pp. 2164-2172, Jun. 2005.

**Images:**

![](https://assets.underline.io/uploads/markdown_image/1/image/2d03b030413a889b83baf91d5cbce4f7.jpg)
Fig. 2. Electromagnetic characteristic according to rotor eccentricity: (a) radial flux density, (b) tangential flux density, (c) induced voltage of 8-pole 12-slot model, and (d) induced voltage of 8-pole 9-slot model.

![](https://assets.underline.io/uploads/markdown_image/1/image/635b8854d507f44663db24dca5394364.jpg)
Figs. 1. (a) Experimental setup, and (b) manufactured test motor.

 Analytical Study and Comparison of Electromagnetic Characteristics of 8-Pole 9-Slot and 8-Pole 12-Slot Permanent Magnet Synchronous Machines According to Rotor Eccentricity

Permanent magnet machines are now-a-days very popular in electric traction applications requiring a wide constant-power speed range. However, the field weakening action, necessary in higher speeds creates important air gap field distribution distortion and increased losses leading to particular configurations search, such as conjunction with variable reluctance rotors [1], pole shoe configurations [2], flat embedded magnet topologies [3], convenient stator windings and permanent magnet arrangements [4], axial flux topologies [5]. In the present paper a convenient configuration of stator windings in permanent magnet motors is proposed involving appropriate additional end winding magnetic circuits in order to achieve inductance management. Such a technique can be applied in all permanent magnet motor configuration cases and enables increased flux weakening capability in high rotor speeds, resulting in substantial efficiency improvements. The optimal design of these extra iron cores can be modeled by adopting a particular reduced scalar potential formulation and the resulting finite element model can be facilitated considering appropriate two dimensional configurations. The overall analysis is performed through co-simulation of the additional magnetic circuits simultaneously with the permanent magnet synchronous machine active part. The proposed methodology enables appropriate handling of increased flux weakening effects in traditional surface mounted permanent magnet motors. It exploits the end zone part of the windings, which does not contribute in the machine torque and performance. The main concept involves introduction of convenient magnetic circuits in the end zone parts of stator coils. These magnetic circuits enable magnetic coupling with auxiliary windings which are connected to appropriate varistors and are energized in desired electromotive force values developed at specific speed ranges through convenient selection of turns ratios. The magnetic material proposed for the additional magnetic circuits is a particular Ferrite ensuring low losses in order not to compromise the machine efficiency. Moreover, the increase of the stator windings leakage inductance is reduced when the auxiliary windings are not energized and is greatly increased when the varistors are activating them. The representation of such configurations necessitates in general a 3D finite element modeling of the whole machine, which is very demanding in computational means. However, an important reduction in computation requirements can be achieved by adopting an appropriate reduced scalar potential formulation, involving one unknown per node. A further calculation simplification can be obtained by implementing an appropriate two dimensional axisymmetric representation for the additional magnetic circuits in conjunction with a two dimensional Cartesian representation of the motor active part and by adopting a direct coupling of field and circuit equations [6]. The methodology developed has been applied in a permanent magnet synchronous machine case with surface permanent magnet rotor configuration and rated power of 100 kW. The motor end winding geometry for one pole part illustrating the additional ferrite toroidal magnetic circuits positioning is shown in Fig. 1. The obtained efficiency maps in cases without and with the additional magnetic circuits are shown in Figs. 2a and 2b, respectively, illustrating the important efficiency improvement resulting in high speed ranges. It may be noted that the proposed technique can offer great services in field weakening action and respective efficiency improvements at high speed ranges of all permanent magnet machine configurations implemented in electric traction applications.

**References:**

 [1] C. Tang, W.L. Soong, T.M. Jahns, et al., IEEE Transactions on Industry Applications, Vol. 51, p.3761 (2015) [2] N. Zhao and N. Schofield, IEEE Transactions on Magnetics, Vol. 53, p. 8112607 (2017) [3] S. Chaithongsuk, B. Nahid-Mobarakeh, J.P. Caron et al., IEEE Transactions on Industrial Electronics. Vol. 59, p.2484 (2012) [4] M.S. Toulabi, J. Salmon and A.M. Knight, IEEE Transactions on Industry Applications, Vol. 53, p.1892 (2015) [5] A. Hemeida, M. Taha, A. Abdallh, et al., IEEE Transactions on Energy Conversion, Vol. 32, p.111 (2017) [6] E. Karamanis and A. Kladas, 2020 International Conference on Electrical Machines (ICEM), p.332 (2020).

**Images:**

![](https://assets.underline.io/uploads/markdown_image/1/image/f741435f33fa0354a4568d7a094b7f78.jpg)
Fig. 1 Stator windings end zone geometry of one pole part of the machine illustrating the additional magnetic circuits positioning.

![](https://assets.underline.io/uploads/markdown_image/1/image/df6370cc71b7cdd695a934844fa86ae8.jpg)
Fig. 2 Efficiency maps of the permanent magnet motor in cases (a) without additional end winding magnetic circuits (b) with additional end winding magnetic circuits.

 Particular Reduced Scalar Potential Formulation for End Winding Magnetic Circuits modeling enabling increased Field Weakening in PM motors

Introduction: Time-step finite element method is widely used in the transient simulation because the harmonic of magnetic fields and the nonlinear characteristics of the material can be processed simultaneously [1]. However, the steady-state solution of the transient simulation convergence slowly due to the time constant characteristic in field-circuit coupling computation [2-3]. Aiming at this problem, this paper proposes an acceleration method based on the estimation of initial values in time step simulation by time harmonic analysis. With the precalculated initial solution, the iteration steps for each point calculation and time for convergence to the steady state are effectively saved. Meanwhile, the advantages of the traditional time step method are well retained. A permanent magnet assisted synchronous reluctance motor (PM-assisted SynRM) is investigated by the proposed method. The comparison results with traditional FEM demonstrate the effectiveness of the proposed method in reducing the iterations step for searching a steady-state solution in the transient simulation. The proposed approach: Firstly, the governing equation for the electromagnetic field can be formulated as equation (1) in Fig. 1. The problem formula also includes the following two equations (2) and (3) in Fig. 1, which describe the connection of the circuit. We can establish field-circuit coupling equations through (1), (2), and (3). Secondly, in time-harmonic analysis, time dependence can be eliminated from the equations by using complex field quantities (4) in Fig. 1. By Galerkin discretization in time-harmonic, the weak formulas (1) and (3) are formed into (5) and (6) in Fig.1. The complex system of equations can be written in the matrix form (7), (8), (9), and (10) in Fig.1. Newton's method is adapted for the nonlinear solution. Taylor expansion is applied to the Jacobian matrix as (11) and (12) in Fig.1 to satisfy the Cauchy-Riemann differential equations. The unknown vector in the time-harmonic simulation is then solved by (13) in Fig. 1 iteratively and only a small number of steps is required for convergence. In the harmonic analysis, the vector potential a can be described as a periodic function in Fig1. (14). The achieved time-harmonic solution is then transferred into the time domain system (16) according to (15) as the initial value at t =0s. Since the time-harmonic simulation results are very close to the steady-state solution in the transient simulation, the iteration for each time-stepping solution can be fast with fewer steps than the traditional method. Also, the time step required for convergence to the steady-state is shortened further. Thereby the total calculation time significantly reduced. The effectiveness of the presented method is verified by the following simulation case. Numerical example: Fig. 2 (a) illustrates the mesh diagrams for the FE model of the PM-assisted SynRM. The time-step simulation is performed at a frequency of 100Hz, and the motor is power by a sinusoidal voltage source with 350V RMS line voltage and -28.3 load angle. Two simulation models run in Matlab on the same workstation. The total cost for the 0.3s simulation of the traditional time-stepping method and the proposed method is 58 mins and 16 mins, respectively. As shown in Fig. 2 (b), the simulation convergence to steady-state at 0.15s, and the corresponding computation cost is 8.5 mins, which means the proposed method is 6 time faster. The good agreement of both methods in steady-state torque calculation in Fig. 2 (b) also demonstrates the accuracy of the proposed method. Conclusion: The effectiveness of the proposed method is verified by the PM-assisted SynRM example. Moreover, due to the universality of the model derivation, it is also applicable to other electrical machines e.g. induction machines.

**References:**

[1] Shinji Wakao, Masato Tokuhisa, and Atsushi Maeda, “ Acceleration of convergence characteristics of time-stepping FE analysis for rotating machines,” IEEE Trans. Magn., vol.37, no.5, pp. 3558–3561, 2001. [2] W. N. Fu, S. L. Ho, and Ping Zhou, “Reduction of computing time for steady-state solutions of magnetic field and circuit coupled problems using time-domain finite-element method,” IEEE Trans. Magn., vol. 48, no. 11, pp. 3363–3366, 2012. [3] Oszkár Bíró and Kurt Preis, “An efficient time-domain method for nonlinear periodic eddy current problems,” IEEE Trans. Magn., vol. 42, no. 4, pp. 695–698, 2006.

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Fig. 1

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Fig. 2

 An Acceleration Method for Reaching Steady-State Performance in Time-stepping Finite Element Analysis

I. Introduction Axial flux permanent magnet (AFPM) machines are getting popularity in various applications. Due to the complex structure of the AFPM machine, 3 dimensional finite element analysis (3D FEA) is normally employed [1]. In order to save the computation time, several 2D FE modelling approaches have been adopted and studied by researchers. 2D linear motor approach (LMMA) is commonly used not only in the performance calculation but also in the analytical study [2]. 2D inner rotor modelling approach (IRMA) and 2D outer rotor modelling approach (ORMA) are proposed and compared with LMMA in [3]. Generally, 2D FE modelling approaches use the geometrical parameters at the average radius of the machine. Considering the variation of geometrical parameters along radial direction, geometrical parameters at different radius are taken into account by the multi-layer 2D FE modelling approaches [3, 4]. However, errors are still existed between the results gotten by 2D FEA and 3D FEA. In order to shorten the computation time and to ensure the accuracy, a 3D FE modeling approach based on scaling air gap method is proposed in this paper. II. The Principle of the Scaling Air Gap Method Basing on the expression of reluctance, the changing of geometrical parameters of an element can be balanced by the adjustment of its relative permeability. In the 3D FE modelling of an AFPM machine, the resizing of the air gap has no influence on the sizes of the other parts. It provides an opportunity to customize the air gap with equivalent relative permeability. If the air gap length is scaled to k (k＞1) times, its relative permeability in axial direction should be adjust to k times and its relative permeability in circumferential and radial direction should be adjust to 1/k times. The electromechanical energy conversion happens in the air gap, so the meshing of the air gap region is very important. Sometimes the air gap may be over meshed due to its small dimension. At this time, the scaling air gap method provides a way to reduce the number of meshes and to refine the meshing quality. III. Comparison among FEA Approaches and Experiments All the 2D and 3D FEA approaches for AFPM machines are implemented to a double-stator single-rotor AFPM machine. In this paper, we focus on the computation time and accuracy of motor performance including back electromotive force (EMF), torque output, and torque ripple. All the 2D FEA is based on multi-layer model to consider the variation of geometrical parameters at different radii. In order to make the study comprehensive, motors with different slot-pole combinations and magnet shapes are employed. Taking a 30-pole 36-slot motor with fan-shape magnets as an example, the comparison based on mesh profile and computation time are presented in Table 1. The comparison of motor performance is shown in Figure 1. It illustrates that all the 2D FEA approaches have advantages in the computation time, but there is a decrease in accuracy. The proposed 3D FEA approach based on scaling air gap method can reduce the computation time with good accuracy compared with the traditional 3D FEA approach. For further verification of the proposed method, a prototype is manufactured and tested. IV. Conclusions A 3D FE modelling approach for calculating AFPM machines based on scaling air gap method is proposed in this paper. The axial length and relative permeability of the air gap can be changed based on the scaling air gap method. In this way, the mesh setting for the air gap will be more flexible and the mesh of the whole machine can be adjusted to be more reasonable. The proposed approach is proved to have shorter computation time than the traditional 3D FEA approach and to be more accurate than 2D FEA approaches. The accuracy of the proposed approach is also verified by experiments.

**References:**

[1] S. H. Won, J. Choi, and J. Lee, "Axial-Gap Type Permanent Magnet Motor Modeling for Transient Analysis," IEEE Trans. Magn., vol. 44, no. 11, pp. 4085-4088, Nov. 2008. [2] F. Zhao, T. A. Lipo, and B. Kwon, "A Novel Dual-Stator Axial-Flux Spoke-Type Permanent Magnet Vernier Machine for Direct-Drive Applications," IEEE Trans Magn., vol. 50, no. 11, pp. 1-4, Nov. 2014. [3] M. Gulec, M. Aydin, "Implementation of different 2D finite element modelling approaches in axial flux permanent magnet disc machines," IET Electr. Power Appl., vol. 12, no.2, pp. 195-202, 2018. [4] C. Bianchini, F. Immovilli, E. Lorenzani, etc., "Axial flux permanent magnet machine desing and optimization using multi-layer 2-D simulation," in Proc. Ann. Conf. Ind. Electron. Soc., 2013, pp. 2620-2625.

**Images:**

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 A Novel 3D Finite Element Modelling Approach for Calculating Axial Flux Permanent Magnet Machines Based on Scaling Air Gap Method

Introduction: Nowadays, with the rapid development of the computer science, numerical methods have been widely used during all the design stages of an electrical machine, such as the electromagnetic design, mechanical structure optimization, thermal estimation etc. We may select the main dimension of the motor, according to the existing electromagnetic design scheme of the induction motor with the same power level. This approach is suitable for the conventional induction motor design, because the main performance is highly determined by the main dimension [1]. However, different from traditional induction motors, the water friction losses of wet submersible motors are much greater than the wind mill losses of air-cooled induction motors. As shown in Fig 1, unlike traditional industrial motors, submersible motors have a larger ratio of diameter to shaft Length The water wear of the water-filled submersible motor accounts for a large proportion of the overall losses, so how to reduce the water wear of the submersible motor has become the key to improving the efficiency of the submersible motor. Many scholars have put forward the numerical calculation method of water wear of water-filled submersible motor, which are shown in Formula (1)-(4) in Figure 2 [2-3]. It can be seen that the main factors affecting the water wear of submersible motors are the surface roughness of the rotor, rotor speed, outer diameter of the rotor and motor shaft length. The literature [4] verified the influence of surface roughness on water wear. For a submersible motor with a given output power, the speed and surface roughness are constant. In this paper, the diameter and shaft length ratio of the motor are optimized to achieve the purpose of reducing the water wear in the design stage. Optimization Method: It can be known from the main relation formula of AC motor that the motor power with constant effective volume of rotor is also approximate. Therefore, keeping the effective volume of the rotor constant, reducing the outer diameter of the rotor and increasing the shaft length can ensure the output power and reduce the water wear of the motor. However, reducing the water wear through the above methods will also increase the electrical losses of the motor. In this paper, the electrical losses of a series of size motors are solved by electromagnetic simulation, and the curve of electrical losses as a function of the rotor outer diameter is fitted by the cubic spline interpolation. A new curve is obtained by adding the water wear and electrical losses of the motor, and the minimum of the curve is the optimal rotor outer diameter. Results: As shown at point M in Fig.2, when the rotor outer diameter is 0.183 m, the sum of electrical losses and water wear of the motor are the minimum. Compared with the loss when the outer diameter of the rotor is 0.225, the loss is reduced by 360 W. This method realizes the optimization of the diameter-axle-length ratio of the submersible motor and reduces the water wear of the submersible motor in the design stage. Detailed results and discussion will be given in the full text.

**References:**

[1] J. Pyrhonen, T. Jokinen, and V. Hrabovcova. Design of Rotating Electrical Machines, 2nd ed. Hoboken, NJ, USA; wiley, (2014). [2] S. Li and S. Liu, Pump Technol., vol. 33, pp. 21–25(1988). [3] H. Liu, M. Tan, and S. Yuan, Trans. Chin. Soc. Agricult. Eng., vol. 22, pp. 107–109(2006). [4] X. He , W. Jiao , C. Wang , et al. IEEE Access, vol. 7, pp. 105331-105341(2019).

**Images:**

![](https://assets.underline.io/uploads/markdown_image/1/image/4e584412cd93d4f18a9970cc97483c8a.jpg)
Fig. 1 A submersible motor with large ratio of diameter to shaft length.

![](https://assets.underline.io/uploads/markdown_image/1/image/ec1237c7417ea9ffc06e457d88d0505b.jpg)
Fig. 2 Losses at different rotor outer diameters.

 Efficiency Improvement for Submersible Motors by Optimizing the Ratio of Diameter to Shaft Length

This paper proposes an equivalent magnetic network (EMN) model for predicting the electromagnetic performances of hybrid excitation machines. In addition to the influence of flux leakage and iron saturation, the proposed EMN model also takes the change of rotor position into consideration. A new node connection method is proposed to make the dynamic analysis easier. Moreover, the reasonable simplification of stator yoke and teeth further reduces the calculation time and ensures the accuracy of the proposed EMN model.In addition, the proposed model in the motor hybrid excitation part can consider the electromagnetic characteristics under different DC excitation conditions. Finally, the prototype is manufactured, and the effectiveness of the EMN model is verified by comparison with the finite-element analysis (FEA) and experimental tests. I.Introduction Hybrid excitation machines not only has many advantages of permanent magnet machine, but also has the advantages of smooth and adjustable air gap magnetic field, wide speed range in electric operation, and wide voltage regulation ability in power generation operation [1]. Therefore, it has received a lot of attention from scholars. In order to analyze the performance of the machine, the finite-element analysis (FEA) method is usually used [2]. However, the hybrid excitation machine is a three-dimensional magnetic circuit structure, which requires a large number of grids, which is very time-consuming. In order to reduce the calculation time, the analytical method is also used to reveal the machine performance [3]. However, the effect of iron saturation is mostly considered, resulting in low accuracy. The equivalent magnetic network method has attracted more and more attention due to its short calculation time and moderate accuracy. In this paper, a dynamic magnetic network analysis model is proposed to predict the electromagnetic performance of consequent pole hybrid excitation machines. The EMN model considers the magnetic flux leakage, the nonlinearity saturation of iron materials and the magnetic bridge, which has high calculation accuracy. The calculated results are compared with the FEA and experimental test results. II.PROPOSED EMN MODEL FOR HYBRID EXCITATION MACHINES Generally, the yoke and tooth magnetic circuit of the machine is regular, and the Simplified EMN modeling method can be used to establish the model. However, the tooth tip, air gap and magnetic bridge magnetic circuit are irregular, and complex magnetic network needs to be established to improve the accuracy and be used for dynamic analysis. At the same time, the DC excitation source should be considered when the hybrid excitation motor is built for three-dimensional magnetic circuit. Figure 1 shows the topology of the machine. The following is a brief introduction to the modeling process: A.Simplified Stator EMN Model The magnetic circuit of the yoke and teeth of the stator is regular. Therefore, a simplified stator EMN model can be used to reduce the calculation time without affecting the accuracy requirements. B. Air Gap EMN Model and Dynamic Analysis The tooth tip of the machine is seriously saturated due to the quasi-closed slot. It is necessary to consider the influence of saturation in order to establish the cross-shaped mesh model. The air gap is the key part of the model, which connects the stator and the rotor. In the dynamic analysis, the stator and rotor depend on the air gap EMN model node connection. It is important to consider the rotor position change with time for the dynamic analysis. Therefore, it is necessary to build cross-shaped mesh model in the air gap. This makes dynamic analysis more effective and faster. C. EMN Model of Rotor and Hybrid Excitation Part When modeling the rotor part, the saturation of the magnetic bridge part is serious, and the cross-shaped mesh model needs to be established. Under the influence of DC excitation, the iron-pole generates magnetic field in the hybrid excitation section of the machine. The permanent magnet and DC magnetic source can be considered separately in the modeling to avoid the complex situation caused by two magnetic sources in the model. It should be noted that the alternating existence of permanent magnet and iron-pole also makes the modeling difficult. III.Results Verification In order to verify the effectiveness of the proposed EMN model, a hybrid excitation machine prototype is developed. The experimental test platform is shown in Fig. 2. The electromagnetic performances, such as the air-gap field distribution, phase flux linkage and back-electromotive force (EMF), d-axis and q-axis inductances, and electromagnetic torque, are predicted by the proposed EMN method. Finally, the results obtained from the EMN method are the compared with those obtained by the FEA and experimental tests. IV.CONCLUSIONS In this paper, an equivalent magnetic network analysis model is proposed to predict the electromagnetic performance of hybrid excitation machine. The new node connection form is established in the tooth tip and air gap for considering dynamic analysis. The proposed EMN model considers the influence of flux leakage and Nonlinear saturation of iron materials. The calculated results are compared with the FEA and experimental test results, which proves the effectiveness of the proposed EMN model. The detailed modeling process and calculation results will be given in the full paper.

**References:**

 [1] Z. Q. Zhu, I. A. A. Afinowi, and Y. Guan, “Hybrid-Excited Stator Slot Permanent Magnet Machines—Influence of Stator and Rotor Pole Combinations,” in IEEE Transactions on Magnetics, vol. 52, no. 2, pp. 1-10, Feb. 2016, Art no. 8100710. [2] K. Wang, J. Li, and C. Liu, “Novel hybrid-pole rotors for consequent-pole PM machines without unipolar leakage flux,” IEEE Trans. Ind. Electron., vol. 66, no. 9, pp. 6811–6823, Sep. 2019. [3] S. G. Min, and B. Sarlioglu, “Fast and systematic design optimization of surface-mounted PM machines using advanced analytical models and subharmonic elimination methods,”IEEE Trans. Magn., vol. 55, no. 1, Jan. 2019, Art. no. 8100216.

**Images:**

![](https://assets.underline.io/uploads/markdown_image/1/image/b80f9b7b361e759844d752bbbfdd52dc.jpg)
Fig. 1. Topology of hybrid excitation machine. (a) Topology of stator. (b) Topology of rotor.

![](https://assets.underline.io/uploads/markdown_image/1/image/bb6ec34b1f0fdd2d048e55985615523c.jpg)
Fig.2.Test platform of a hybrid excitation prototype.

 Electromagnetic Performance Analysis of a Hybrid Excitation Machine Based on Equivalent Magnetic Network

Nowadays some industrial applications require contactless motion transmission. The use of magnetic couplers is the most appropriate solution. The synchronous version of this solution, based in PM excitation, can be adopted in radial or axial topologies. In these topologies the most common shapes of permanent magnets are rectangular, sector and circular. The electromagnetic torque of a magnetic coupler, required to transmit motion, is usually calculated using numerical methods or even 3D analysis which takes into account all the geometric and physical effects. However, in the design process, you need a fast and precise model that does not require a lot of computation time. Firstly, a purely 3D analytical model for axial coupler (with sector shape magnets), based on magnetic scalar potential formulation, is developed. So, the magnetic field distribution in different regions (PM, air gap and iron disks) leads to solve the Laplace’s equation. In low-permeability sub domains, the fields due to the two PM rotors of the magnetic coupler are calculated separately. The solutions form of the partial differential equations expressed in cylindrical coordinates are determined using the method of separation of variables. Secondly, we extend the above developed model to calculate the field in the magnetic coupler with magnets of rectangular shape. So, it is necessary to divide the geometry of the rectangular magnet into a number of elementary geometric elements where each element is approximated by a sector-shaped one keeping the same volume of magnet. The approach adopted can be summarized as follows:- Subdivide each rectangular Magnet in N radial Elementary Blocks; - Approximate the elementary block by a sector shape with the same volume; - Compute the magnetic Field of each sector shape block with the developed model;- The total magnetic field, torque and axial force are computed by using the superposition principle. Hence, the total torque developed by the magnetic coupler is obtained by summation of all torques produced by the interaction of each block of the first inductor with all blocks of the second inductor. The results obtained by the proposed 3D analytical model are compared to those obtained by 3D finite elements and to those determined experimentally. A close agreement is noticed (relative error on the static torque don’t exceed 2 %) between the measured and the predicted torques, which demonstrates the validity of the proposed model. The low computing time of the developed model provides an efficient and quick tool for assessing the influence of the geometrical and physical parameters of a magnetic coupler as a part of a design optimization process.

**References:**

[1] L. Belguerras and L. Hadjout, "Study of HTS Magnetic Coupler Using Analytical and Numerical Computations" IEEE Trans. Applied Superconductivity, Vol. 24, No. 6, December 2014 [2] Jian Wang and all, "A General Analytical Model of Permanent Magnet Eddy Current Couplings", IEEE Trans. Magn, Vol. 50, No. 1, January 2014. [3] Hyeon-Jae, Shin and all, "Design and Analysis of Axial Permanent Magnet Couplings Based on 3D FEM" IEEE Trans. Magn, Vol. 49, No. 7, JULY 2013. [4] T. Lubin ,S. Mezani and A. Rezzoug, "Simple analytical expressions for the force and torque of axial magnetic couplings". IEEE Trans. on Energy Conversion, volume 27, N°2, pp. 536-546, 11 pages, Juin 2012.

**Images:**
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 Improved 3D Electromagnetic Analytical Model of an Axial Flux Magnetic Coupling with Rectangular Shaped Permanent Magnets

The traditional finite element model of permanent magnet synchronous generator（PMSG） needs nonlinear iteration for each grid, and time-consuming. Besides, the performance of various components of the voltage regulator controller (VRC) will be affected by the operating environment. The traditional component library cannot meet the accurate digital twin effect. Taking an emergency power supply system for an unmanned aerial vehicle as an example, this paper uses the device-level modeling method to build a digital twin simulation model (DTSM) of a PMSG and its AC-DC regulated power supply system, which simulation speed can guarantee real-time output results in synchronization with the experiment, and has an agile digital twin effect. Finally, the calculated results are compared with the experimental values to verify the accuracy of the proposed digital twin device-level model, which is of great significance to the combined design of PMSGs and VRCs. Index Terms：Permanent magnet synchronous generator (PMSG); Digital twin ;Voltage regulator controller. I. Introduction The performance of permanent magnet synchronous generator (PMSG) is closely related to its control method and load characteristics. When the AC-DC step-down chopper voltage stabilization control strategy is adopted, it can ensure the output of stable DC power while reducing the three-phase line current of the generator, reducing the motor winding loss greatly, and optimizing the matching design of the generator and the power converter. The power stabilization system is stable and efficient. Therefore, the research of PMSG and its AC-DC conversion and voltage stabilization system (VSS) simulation can promote the development of PMSG and VSS technology, improve system design accuracy effectively, and realize the perfect match to improve the stability and reliability of the VSS [1][2][3][4]. II. Composition of VSS Circuit After studying the load characteristics and actual working environment, the power supply system adopts a PMSG combined with a three-phase uncontrolled rectifier bridge and a BUCK converter. The actual power supply system consists of PMSG, three-phase uncontrolled bridge rectifier circuit, power regulator circuit, filter circuit, feedback circuit, control circuit, drive circuit and auxiliary power supply circuit. III. Digital Twin Device-Level Simulation Modeling In order to improve the simulation speed of the simulation model and achieve a fast digital twin effect, this paper uses the ECE reduced-order model extraction method to convert the generator finite element model into a data matrix model, and establishes the PWM main control chip SG1525 and the device-level modeling method. The digital twin simulation model (DTSM) of the AC-DC VSS of the PMSG is built as shown in Fig.1. The simulation speed can ensure the real-time output results in synchronization with the experiment results, and realize the fast and accurate digital twin effect. IV. Experimental Verification The PMSG and its VSS were tested on a dedicated test bench, which is shown in Fi.g. 2. The oscilloscope is used to display the output DC voltage waveform in real time, and the DTSM is run on the computer at the same time. The simulation data is highly consistent with the measured data. V. Conclusion This paper proposed a high-precision DTSM based on the actual prototype of an emergency power supply system for an unmanned aerial vehicle. Firstly, the ECE reduced-order mathematical model is extracted by the alternating-direct-axis periodic current scanning method, which accelerates the simulation speed greatly. Secondly, according to the actual circuit structure of the emergency voltage stabilization control power converter, a DTSM of the entire VSS circuit is built. Finally, the accuracy of the DTSM is verified by experiments.The reduced-order model extraction and device-level modeling techniques used in this paper are in line with the development trend of digital twin technology. The research results can provide a reference for the design of PMSG and the optimal matching design of VSS.

**References:**

[1] A. Rassõlkin, V. Rjabtšikov and T. Vaimann. "Digital twin of an electrical motor based on empirical performance model,"2020 XI International Conference on Electrical Power Drive Systems (ICEPDS), Saint Petersburg, Russia, 2020. [2] N. Khaled , B. Pattel and A. Siddiqui. “Digital twin development and cloud deployment for a DC motor control embedded system”, 2020. [3] R. Goraj. “Digital twin of the rotor-shaft of a lightweight electric motor during aerobatics loads”, Aircraft engineering and aerospace technology, 2020. [4] N. Khaled , B. Pattel and A. Siddiqui. “Digital twin development for an inverter circuit for motor drive systems”, Digital Twin Development and Deployment on the Cloud, PP. 163-201, 2020.

**Images:**

![](https://assets.underline.io/uploads/markdown_image/1/image/82e16107aa4d5c0d5770a5259dc1f38a.jpg)
Fig.1. The DTSM of the AC-DC VSS of the PMSG.

![](https://assets.underline.io/uploads/markdown_image/1/image/bccf3f35c4be885acb6e6910cdef3814.jpg)
Fig.2. The test bench of PMSG and its VSS.

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